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International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 27 much work has to be carried out on the analysis, design, control and experimental testing of this machine before the trade-offs in inverter size versus machine size and the subsequent cost issues can be quantified. The main objective of this article is to: • Predict the dynamic and steady-state performances of the BDFRM. • Demonstrate the important aspects of the machine behavior in various modes of operation. • Study the start-up and synchronization process of the BDFRM under V/F control. • Develop a control technique by which the machine can be successfully controlled over a wide range of speeds. 2. MACHINE STRUCTURE The stator configuration of the BDFRM has conventional laminations with 36 uniformly distributed semi-open slots. The rotor, however, is constructed with reluctance saliency. The stator has two separate stationary windings, each one of the windings having a different pole numbers, so that the windings are not magnetically coupled, and the magnetic mutual coupling between the two sets of stator windings is realized through the rotor. Thus, the rotor structure basically determines the magnetic coupling between the two stator windings, which, in turn, determines the machine behavior. Furthermore, to avoid unbalanced magnetic pull on the rotor, the difference between the pole pairs of the two stator windings must be greater than one [7, 11]. Also, the number of salient rotor poles must equal the sum of the number pole pairs in the stator windings. The saliency on the rotor serves only to provide magnetic coupling between the two stator windings. The rotor speed is a function of the frequency of the secondary winding currents. The basic structure of the BDFRM is shown in Figure 1. As can be seen, the primary winding has 2p-pole, and is connected to the main supply, while the secondary (control) winding has 2q-pole, and is connected to an inverter. Figure 1. Schematic diagram of the brushless doubly fed reluctance machine (BDFRM) 3. THE MACHINE MODELING 3.1. Dynamic Model The analysis presented here is based on representing the machine in terms of equivalent rotating reference frame fitted along the d- and q-axes and rotates with rotor speed. The following assumptions are considered:

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 28 • The two stator windings are assumed to have sinusoidally distributed windings having equal turns per phase. • The iron of both stator and rotor has infinite permeability. • Effects of magnetic saturation and core losses are ignored. • Effects of stator slots are neglected. Assuming balanced operating conditions, the voltage equations of the BDFRM in the rotor reference frame can be written in a simplified form as follows [4]: ݒௗ ൌ ݖௗ ݅ௗ (1) The electromagnetic torque is ܶ ൌ ܯଵ൫݅ଵ݅ௗ െ ݅ௗଵ݅൯ ܯݍଶሺ݅ଶ݅ௗ െ ݅ௗଶ݅ሻ (2) which can be written in terms of primary winding parameters as: ܶ ൌ ଷ ଶ ሺ ݍሻሺߣௗଵ݅ଵ െ ߣଵሻ (3) The dynamic equation is given by ܶ ൌ ܬ ௗఠ ௗ௧ ߱ܤ ܶ (4) The subscripts “1,” “2,” and “r” refer to the quantities associated with the primary, the secondary windings and the rotor circuit, respectively. M1 is the mutual inductance between the primary winding and rotor circuit, M2 is the mutual inductance between the secondary winding and rotor circuit, M12 is the mutual inductance between the primary and secondary windings. ωr , J , B, and TL are the rotor angular speed, motor inertia, friction coefficient, and load torque, respectively. ܼௗ ൌ ۏ ێ ێ ێ ێ ێ ێ ێ ێ ۍݎଵ ܮଵ ௗ ௗ௧ ܮଵ߱ ܯଵଶ ௗ ௗ௧ െܯଵଶ߱ ܯଵ ௗ ௗ௧ ܯଵ߱ െܮଵ߱ െݎଵ ܮଵ ௗ ௗ௧ െܯଵଶ߱ െܯଵଶ ௗ ௗ௧ ܯଵ߱ ܯଵ ௗ ௗ௧ ܯଵଶ ௗ ௗ௧ െܯݍଵଶ߱ ݎଶ ܮଶ ௗ ௗ௧ ܮݍଶ߱ െܯଶ ௗ ௗ௧ ܯݍଶ߱ െܯݍଵଶ߱ െܯଵଶ ௗ ௗ௧ െܮݍଶ߱ ݎ ܮ ௗ ௗ௧ ܯݍଶ߱ െܯଶ ௗ ௗ௧ ܯଵ ௗ ௗ௧ 0 െܯଶ ௗ ௗ௧ 0 ݎ ܮ ௗ ௗ௧ 0 0 ܯଵ ௗ ௗ௧ 0 ܯଶ ௗ ௗ௧ 0 ݎ ܮ ௗ ௗ௧ے ۑ ۑ ۑ ۑ ۑ ۑ ۑ ۑ ې (5) ݒௗ ൌ ሾݒଵ ݒௗଵ ݒଶ ݒௗଶ ݒ ݒௗሿ் ݅ௗ ൌ ሾ݅ଵ ݅ௗଵ ݅ଶ ݅ௗଶ ݅ ݅ௗሿ் 3.2. Steady-State Model The steady-state analysis can be obtained by assuming that the machine is synchronized so that the frequencies of the windings in the two axes are constrained by (7), allowing either positive or negative sequence secondary (control) voltage. Maintaining this constraint enables power to flow from one winding to another through the rotor circuit. In response to the stator fields, rotor currents

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 29 are induced at frequencies of ωpr and ωsr . The rotor field can induce emfs in the primary winding at frequency ωp and in the secondary winding at frequency ωs only when ωpr = ωsr . Where ߱ ൌ ߱ െ ߱ and ߱௦ ൌ ߱௦ା ି ߱ݍ (6) Equating both sides of Eq. (6), one obtains the motor speed as: ߱ ൌ ఠ ఠೞశ ష ା (7) Negative sign (−) is used for the motor speed below the synchronous speed and the positive sign (+) is used for the motor speed above the synchronous speed. The steady-state voltage equations can be obtained by replacing d/dt by jω in Eq. (5). The qd variables become phasors and these phasors are related to symmetrical positive and negative sequence components [8–11]. Hence, the steady-state equations may be written as ܸଵ ൌ ሺܴଵ ݆ܺଵሻܫଵ ݆ܺଵଶܫଶ כ ݆ܺଵܫ (8) ௩మ כ ௌ ൌ ቀ ோమ ௌ ݆ܺଶቁ ܫଶ כ ݆ܺଵଶܫଵ ݆ܺଶܫ (9) 0 ൌ ൬ ோ ௌ ݆ܺ൰ ܫ ݆ܺଵܫଵ ݆ܺଶܫଶ כ (10) ܶ ൌ ଷ ଶ ܴ൫݆ܯଵሺܫଵ כ ܫሻ െ ݆ܯݍଶሺܫଶܫሻ 2݆ሺ ݍሻܯଵଶሺܫଵ כ ܫଶ כሻ൯ (11) The electromagnetic torque of Eq. (11) consists of three components: • The first component is due to the interaction between the rotor circuit and the primary stator windings. • The second component is due to the interaction between the rotor circuit and the secondary stator windings. • The third component is due to the interaction between the two stator windings (namely the synchronous torque). Equation (11) is valid only for the BDFRM with cage rotor, but in case of cageless rotor, the first and second components disappear. Using the power winding voltage as a reference, the equivalent circuit voltages can be written as: ܸതଵ ൌ ට ଷ ଶ ܸଵ݁ and ܸതଶ ൌ ට ଷ ଶ ܸଶ݁ఉ (12) where V1 and V2 are the magnitudes of the actual power and control winding phase voltages. β is the angle between the power and control winding voltages. 4. MODES OF OPERATION OF THE BDFRM The modes of operation of the BDFRM may be classified according to the excitation of the control winding into three modes of operation as follows.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 30 4.1. Asynchronous Mode This mode takes place when the primary winding is excited from the main supply with a frequency fp, and the secondary winding is either open circuited or short-circuited. If the secondary winding is short-circuited, currents are induced and these currents interact with the primary flux producing a torque in the rotor. The frequency of these induced currents decreases from fp when the rotor at standstill to zero at the synchronous speed of Ns = 60fp/(p + q). 4.2. Synchronous Mode This mode takes place when the primary winding is fed from the main supply and the secondary winding is connected to a DC supply. For a DC excitation, the common and practical connection of two phases in parallel and one phase in series is used. Also, this mode can take place when the two sets of the stator winding are excited from two separate sources of different frequencies. Synchronous operation is established when the frequencies of the induced current in the rotor produced by the two rotating fields of the stator windings become identical. Once synchronous operation is established, shaft speed becomes independent of load conditions unless a serve disturbance occurs. Synchronization can also be achieved if a set of low frequency, negative sequence AC voltage is applied to the 2-pole winding. In this case, the 2-pole frequency is slowly ramped up, with the 2-pole voltage. The voltage is applied in such a way that a constant V/Hz ratio is maintained. Once the machine is running synchronously, the applied voltage on the 2-pole winding can be reduced to a substantially lower level without losing synchronism. This is a practical importance in certain applications since reducing the excitation voltage means reducing the rating requirements of the power inverter and hence the cost. 4.3. Supersynchronous Mode This mode can be defined as the speed above the synchronous speed of the 6-pole winding field. This mode takes place when the primary winding is connected to the main source and the secondary winding is fed from an inverter with inverting the phase sequence of the secondary winding current. 5. SPEED CONTROL Unfortunately, speed control of the BDFRM did not receive more attention from the researchers . Speed control of the BDFRM can be successfully achieved using field oriented control (FOC) technique which can be applied to either a 6-pole winding or a 2-pole winding depending on the selection of the transformation [22]. The reference frame used for vector control is ω = ω1. Under this condition the primary equation is in the frame ω1, and the secondary equation is in the frame ω2. The electromagnetic torque can be re-written in the following form [17]: ܶ ൌ ଷ ଶ ሺ ݍሻ ெభమ భ ൫ߣௗଵ݅ଶ ߣଶ݅ௗଶ൯ (13) where p, q are the pole pair number of the two stator windings, respectively. Hence, one can further manipulate Eq. (13) to get an expression in terms of the primary fluxes and secondary currents. This expression is particularly useful since the secondary currents are the variables one has control over using an inverter, and the primary fluxes are fixed by the voltage and frequency of the main supply. Equation (13) can be further refined by using the frame ω1 and aligning the primary reference frame so that it lies along the primary flux vector. The primary flux vector can be written as

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 31 ߣଵ ൌ ߣௗଵ ݆ߣଵ (14) Equation (14) means that we have defined away the λq1 flux component and therefore Eq. (13) can be simplified to: ܶ ൌ ଷ ଶ ሺ ݍሻ ெభమ భ ൫ߣଵ݅ଶ൯ (15) where λ1 is the magnitude of the primary flux vector. Equation (15) forms the basis for vector control of the BDFRM. It could be observed that the torque can be controlled by ݅ଶ, while λ1 is a constant related to the main supply conditions. Therefore, it has independent control of the torque. It should be noted that the secondary currents are measured relative to the primary reference frame. Therefore, ݅ଶ is the q-axis component of the secondary winding current. The block diagram of the implemented FOC is given in Figure 2. The scheme consists of an outer speed feedback loop and an inner current loop. The control signals ݅ௗଶ כ and ݅ଶ כ are proportional to the flux and torque commands, respectively. Consequently, ݅ௗଶ כ is the field component of the control winding, while ݅ଶ כ is Figure 2. Block diagram of the implemented FOC. the torque component of the control winding current. The unit vectors cos θ2 and sin θ2 are calculated from the information of rotor position as: θ2 = θ1−(p+q)θr , where θ2 is the secondary current angle, θ1 is the primary flux angle, and θr is the rotor angle. The flux component of current is determined as

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 32 a function of the desired rotor flux and is maintained constant. The torque component of current is derived from the speed control loop. The actual motor currents are compared with its reference waveforms in a hysteresis controller. The output of the hysteresis controller is used to control the inverter switching devices such that the error between the motor actual and reference is acceptable. The indirect vector control gives the advantage of fast transient response because of the linear relation between the torque and iq2. These facilitate the design of the drive for four-quadrant operation. The machine can be started according to the following four steps: 1) The machine is freely accelerated close to the synchronous speed of the primary winding; 2) The inverter is switched into the secondary windings; 3) Speed control is applied to bring the machine to the desired (below or above synchronous) speed; and 4) Once the rotor speed is close to the synchronous speed, the speed control loop is activated. 6. SIMULATION RESULTS Simulation results were obtained using available software package of Matlab/Simulink. 6.1. Run-Up Responses Figure 3 shows the simulated responses of speed and stator currents during free acceleration for the BDFRM when the 6-pole is connected to the main supply, while the 2-pole winding was short-circuited. It can be noted that the responses of the BDFRM are similar to those of conventional 8-pole induction motor runs up to a steady state speed, which is less than 1000 rpm. (a) (b) (c) Figure 3. Run-up responses when the 6-pole winding is connected to the main source and the 2-pole is short-circuited. (a) speed versus time; (b) primary current versus; and (c) secondary current time versus time

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 33 Figure 4 shows the simulated run-up responses of speed for the BDFRM when the 6-pole winding is connected to a 60 V, 50 Hz power supply and the 2-pole winding was open-circuited. It can be seen from the results that the use of rotor cage winding with the BDFRM improves the run-up response and this makes the machine self-starting. The synchronous speed of the 6-pole winding is approximately fixed (1000 rpm) by the current frequency in the 6-pole main winding. The responses are similar to those of conventional 6-pole induction motor runs up to a steady-state speed of 1000 rpm. Figure 5 shows the simulated run-up responses of the motor during DC synchronization. Initially the machine is running steadily in the singly fed induction mode. Synchronization begins when a set of DC voltage (18 V DC) was applied to the initially short-circuited 2-pole winding. It can be noted from the results that the motor can pull into synchronism quickly and runs steadily at 750 rpm, yielding a good synchronization process. The responses are similar to those of a conventional 8-pole synchronous motor. Figure 6 shows the simulated speed-time response when the motor is running in the Supersynchronous mode. It is clear from the figure that the motor speed Figure 4. Run-up speed responses when the 6-pole winding is connected to the main source and the secondary winding is open circuited increases with increasing the secondary current frequency. This can be achieved when the two stator windings having the same sequence. Figure 7 shows the simulated speed-time response when the motor is singly-fed from the 6- pole winding under (V/Hz) control. In such a case, the 2-pole winding was left open. Base voltage and frequency are taken to be 60 V and 50 Hz, respectively. When the conventional PWM inverter drives the line-start BDFRM, the terminal voltage can be changed easily for high efficiency operation. Figure 8 shows the simulated speed-time response when the motor is singly-fed from the 2- pole winding under (V/Hz) control. Base voltage and frequency are chosen to be 120 V and 16.67 Hz, respectively. In this case, the 6-pole winding is left open. It is noticed from Figure 9 that motor speed reached 1000 rpm, while if the base frequency was chosen to be 50 Hz, then the speed will reach 3000 rpm.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 34 Figure 5. Run-up speed responses for a synchronous mode of operation Figure 6. Run-up responses for a Supersynchronous mode of operation Figure 7. Run-up speed response for the 6-pole winding under (V/Hz) control when the 2-pole winding is open-circuited

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 35 Figure 8. Run-up speed response for the 2-pole winding under (V/Hz) control at secondary current frequency 16.67 Hz and the 6-pole winding is left open Figure 9 shows the rotor speed response when the drive is subjected to a step increase in the reference speed from 1000 rpm to 1500, 1800, and then 2400 rpm, respectively. It can be seen from the results that the actual speed of the machine overlaps the command speed, showing a perfect speed tracking. For Supersynchronous speeds, the sequence of the secondary winding must be inverted with increasing the input command of the 2-pole winding. Therefore, any desired speed can be achieved by increasing the step in reference speed. Figure 9. Speed versus time response to step increase in the reference speed Figure 10 shows the speed and secondary current responses when the drive is subjected to a step decrease in the reference speed from 1500 rpm to 1200, 900, 600, and then 300 rpm, respectively. It is clear from the results that the actual speed of the machine follows the command speed showing a good speed tracking.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 36 Figure 10. Speed versus time response to step decrease in the reference speed. Figure 11 shows the simulated speed and secondary current responses of the drive system when a step change in the load occurs while the machine was running at a steady speed of 600 rpm. It can be noticed from the figure that the speed response increased and then decreased so that it could be returned back to its steady-state value after removing the load. On the other hand, the secondary current is decreased to the no-load value. In general, the proposed controller exhibits a good transient response and high control accuracy with the BDFRM. The controller also provides convenience for tuning control parameters. Figure 11. Speed and secondary current responses during a sudden change in the load. (a) speed versus time; (b ) secondary current versus time.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 37 7.2. Steady-State Performance Steady-state performance predictions can be obtained using the steady-state model presented in Section 3.2. In order to examine the validity of the model, simulation of the steady-state performance of a 0.75 hp, 6/2-pole stator with a 4-pole reluctance rotor machine was used. The self and mutual inductances of the BDFRM can be determined analytically in standstill condition of the machine as [17]: ܮଵ ൌ ඥሺܸଵ ܫଵ⁄ ሻଶ െ ሺܴଵሻଶ /߱ଵ (16) ܯଵଶ ൌ ቀ మ ூభ ቁ ߱ଵൗ (17) where V1 and I1 are the phase voltage and current are applied to the 2p-pole winding, and V2o is the measured open-circuit phase voltage of the 2q-pole winding. In a similar way, the self-inductance L2 and mutual inductance M21 can be determined. It should be noted that the self-inductance and mutual inductance are dependent on the rotor position. Figure 12 shows the measured self-inductance and mutual-inductance curves versus the rotor position angle of the BDFRM. For the sake of clarity, only the inductance of one phase for the 6-pole winding and one phase for the 2-pole winding is displayed. The results show that the self-inductance and mutual inductance of the primary and secondary windings do not have much difference. Figure 13 shows the variation of the primary winding power factor angle as a function of the control voltage at different values of the secondary current frequency. It can be seen from Figure 14 that the machine has the ability to control the primary power factor from leading to lagging via the secondary voltage and its frequency Figure 14 shows the variation of the primary power factor as a function of the control voltage at different values of the secondary current frequency. The results show that the power factor can be improved by varying the secondary voltage. Notice that the primary power factor improves reaching its maximum value at Vs = 40 V when the secondary winding becomes fully responsible for the flux production. Behind this value, the power factor decreases towards zero as the primary winding is generating large amounts of reactive power into the grid, this being taken by the secondary winding from the inverter. Figures 15 and 16 show the variations of primary and secondary stator currents as a function of the secondary control voltage at different values for the 2-pole winding current frequency. It is noticed that the secondary winding currents increase with increasing the control voltage. However, it is observed that the primary stator current of a BDFRM exhibits a characteristic of a V curve when the control voltage is increased. This unique feature can be used successfully to improve the power factor of the BDFRM. The minimum power winding currents, which correspond to the highest power factors possible, is evident. The similarity between the V curves of a BDFRM and those of a conventional synchronous motor is observed.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 38 Figure 12. variation of inductances with rotor position angle

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 39 Figure 13: variation of the primary winding power factor angle with control voltage Figure 14: variation of the primary power factor with control voltage

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 40 Figure 17 shows the variation of the overall power factor of the machine as a function of the control voltage at different values of the secondary current frequency. The results show that the overall power factor of the BDFRM improves reaching its maximum value at Vs < 20 V when the primary and secondary windings are responsible for the flux production. Figure 15. Variation of the primary winding current with control voltage Figure 16. Variation of the secondary winding current with control voltage

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 41 Figure 18 shows the variation of the efficiency as a function of the control voltage at different values of the secondary current frequency. It can be noticed that the efficiency of the BDFRM improves with increasing of both control voltage and secondary current frequency. The symbols shown in Figures 14 through 19 are related as: + for ೞ ൌ 0.01 * for ೞ ൌ 0.1 - for ೞ ൌ 0.15 Figure 17. Variation of the overall power factor with control voltage Figure 18. Variation of the efficiency with control voltage

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 42 8. CONCLUSION A successful analytical design of a BDFRM has been developed and tested in different modes of operation. It is designed to operate at both line and variable frequencies. Moreover, performance analysis of such a machine has been given. A comprehensive set of results for the digital simulation of the run-up and steady-state performances of such type of motors has been extensively presented. the results showed that the BDFRM has performance characteristics similar to those of a non-salient pole synchronous machine. Effects of both voltage and frequency of the control winding on the machine performance have been investigated. It was noticed that the rating of the control winding and the inverter is a function of the required operating conditions of speed and power factor of the power winding. Simulation results have been illustrated improved system performance under V/Hz control. A speed control method for the BDFRM was developed and successfully tested. The main advantage of the proposed drive is its improving capability to operate at any desired speed including standstill condition. The proposed controller exhibits a good transient response and high control accuracy with the BDFRM. The controller also provides convenience for tuning control parameters. A This article conclusively proves that the BDFRM still needs a lot of research and improvement for the practical use. Therefore, additional analysis to account for core and stray load losses in the BDFRM is being under taken. REFERENCES [1] A. Broadway and L. Burbridge, “Self-cascaded machine: A low speed motor or a high frequency brushless alternator,” Proc. IEE, vol. 117, pp. 1277–1290, July 1970. [2] A. Broadway, B. Cook, and P. Neal, “Brushless cascade alternator,” Proc. IEE, vol. 121, pp. 1529–1535, December 1974. [3] F. Liang, L. Xu, and T. Lipo, “d-q analysis of variable speed doubly AC excited reluctance motor,” Electric Machines and Power Systems, vol. 19, pp. 125–138, March 1991. [4] L. Xu, F. Liang, and T. Lipo, “Transient model of a doubly excited reluctance motor,” IEEE Trans. on Energy Conversion, vol. 6, pp. 126–133, March 1991. [5] R. Li, A. Wallace, and R. Spee, “Two-axis model development of cage-rotor brushless doubly fed machines,” IEEE Trans. Energy Conversion, vol. 6, pp. 453–460, September 1991. [6] L. Xu and Y. Tang, “A novel winding-power generating system using field orientation controlled doubly-excited brushless reluctance machine,” Proceedings of the IEEE IAS Annual Meeting, pp. 408–418, 1992. [7] C. S. Brune, R. Spee, and A. K. Wallace, “Experimental evaluation of a variable-speed doubly fed wind-power generation system,” IEEE Trans. IEEE, vol. 30, pp. 648–655, May/June 1994. [8] R. Li, R. Spee, A. K. Wallace, and G. C. Alexander, “Synchronous drive performance of brushless doubly fed motors,” IEEE Trans. IAS, vol. 30, no. 4, pp. 963–970, July/August 1994. [9] M. S. Boger, A. K. Wallace, R. Spee, and R. Li, “General pole number model of the brushless doubly fed machine,” IEEE Trans. IAS, vol. 31, no. 5, pp. 1022–1027, September/October 1995. [10] B. V. Gorti, G. C. Alexander, and R. Spee, “Power balance considerations for brushless doubly fed machines,” IEEE Trans. on Energy Conversion, vol. 11, no. 4, pp. 687–692, December 1996.

International Journal of Electrical Engineering and Technology (IJEET), ISSN 0976 – 6545(Print), ISSN 0976 – 6553(Online) Volume 5, Issue 2, February (2014), pp. 26-43 © IAEME 43 [11] M. M. A. Ahmed, Mixed Pole Machines, Ph.D. Thesis, Alexandria University, Faculty of Engineering, 2001. [12] Y. Liao, L. Xu, and L. Zhen, “Design of a doubly fed reluctance motor for adjustable-speed drives,” IEEE Trans. IAS, vol. 32, pp. 1195–1203, September/October 1996. [13] R. Betz and M Javanovic, Introduction to brushless doubly fed reluctance machines—The basic equations, Tech. Report, Dept., Elect. Energy Conversion, Aalborg University, Denmark, April 1998, Available at http://HYPERLINK http://www.ee.newcastle www.ee.newcastle.edu.au/users/ staff/reb/Betz.html. [14] R. Betz and M Javanovic, “The brushless doubly fed reluctance machine and the synchronous reluctance machineA comparison,” Proceedings of the IEEE—IAS Annual Meeting, October 1999. [15] R. Bentz and M. Jovanovic, “Theoretical analysis of control properties for the brushless doubly fed reluctance machine,” IEEE Transactions on Energy Conversion, pp. 332–339, September 2002. [16] A. Munoz-Garcia and T. A. Lipo, “Stator winding induction machine drive,” IEEE Trans. IAS, vol. 36, pp. 1369–1379, September/October 2000. [17] F. Wang, F. Zhang, and L. Xu, “Parameter and performance comparison of doubly fed brushless machines with cage and reluctance rotors,” IEEE Trans. IAS, vol. 38, no. 5, pp. 1237–1243, September/October 2002. [18] Haider M. Husen , Laith O. Maheemed and Prof. D.S. Chavan, “Enhancement of Power Quality in Grid-Connected Doubly Fed Wind Turbines Induction Generator”, International Journal of Electrical Engineering & Technology (IJEET), Volume 3, Issue 1, 2012, pp. 182 - 196, ISSN Print : 0976-6545, ISSN Online: 0976-6553. [19] Nadiya G. Mohammed, HaiderMuhamadHusen and Prof. D.S. Chavan, “Fault Ride-Through Control for a Doubly Fed Induction Generator Wind Turbine Under Unbalanced Voltage Sags”, International Journal of Electrical Engineering & Technology (IJEET), Volume 3, Issue 1, 2012, pp. 261 - 281, ISSN Print : 0976-6545, ISSN Online: 0976-6553. [20] B.Sivaprasad, O.Felix, K.Suresh, G.Pradeep Kumar Reddy and E.Mahesh, “A New Control Methods for Offshore Grid Connected Wind Energy Conversion System using Doubly Fed- Induction Generator and Z-Source Inverter”, International Journal of Electrical Engineering & Technology (IJEET), Volume 4, Issue 2, 2013, pp. 305 - 323, ISSN Print : 0976-6545, ISSN Online: 0976-6553.

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40220140502005

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